Wireless power transfer using multiple near-field plates

ABSTRACT

A near-field plate is a non-periodically patterned surface that can overcome the diffraction limit and confine electromagnetic fields to subwavelength dimensions. By controlling the interference of the electromagnetic fields radiated by the near-field plate with that of a source, the near-field plate can form a subwavelength near-field pattern in a forward direction, while suppressing fields in other directions, such as those reflected. The resulting unidirectional near-field plate may find utility in many applications such as high resolution imaging and probing, high density data storage, biomedical targeting devices, and wireless power transfer.

CROSS-REFERENCE TO RELATED APPLICATION

This application is a continuation-in-part of U.S. application Ser. No. 14/687,874, entitled “Unidirectional Near-Field Focusing using Near-Field Plates,” filed Apr. 15, 2015, which claims the benefit of U.S. Provisional Application No. 61/980,109, entitled “Unidirectional Near-Field Focusing using Near-Field Plates,” filed Apr. 16, 2014, both applications of which are hereby incorporated herein in their entirety.

FIELD OF THE DISCLOSURE

The present disclosure relates to techniques for manipulating the electromagnetic near field and, more particularly, to techniques for unidirectional subwavelength near-field focusing using near-field plates.

BACKGROUND

The background description provided herein is for the purpose of generally presenting the context of the disclosure. Work of the presently named inventors, to the extent it is described in this background section, as well as aspects of the description that may not otherwise qualify as prior art at the time of filing, are neither expressly nor impliedly admitted as prior art against the present disclosure.

An electromagnetic beam with subwavelength beamwidth and low sidelobes is important to the operation of a wide array of electromagnetic devices. High resolution probes, sensors and imaging systems, high density data storage devices, lithography systems, biomedical targeting devices, and wireless power transfer systems are a few examples of such devices.

Although subwavelength electromagnetic confinement is necessary for these devices, electromagnetic confinement can only be obtained at extremely close distances, due to the diffraction limit. Stated differently, such confinement is only possible at extremely close distances where evanescent components exist. Such confinement requirement is difficult to meet in many applications and limiting for many devices. For example, a subwavelength probe placed in close proximity of a biomedical sample can distort both the sample and the measurement results. As a result, there is growing interest in a method that can overcome the diffraction limit at extended operating distances.

Over a decade ago, metamaterial superlenses were proposed as a possible solution by J. B. Pendry, Phys. Rev. Lett., 85, 3966, 2000. Metamaterial superlenses can enhance and recover the evanescent spectrum to overcome the diffraction limit over an extended range. Accordingly, they held great promise for improving the performance of near-field devices and their proposal was followed by numerous publications. Several metamaterial superlenses were experimentally demonstrated and their ability to overcome the diffraction limit and obtain super-resolution was verified. However, the proposed metamaterial superlenses were limited by loss, narrow frequency bands of operation, polarization dependence, and fabrication challenges.

More recently, an alternative method to overcome the diffraction limit has been proposed, which relies on the interference of highly oscillatory electromagnetic fields to form subwavelength patterns as discussed by R. Merlin, Science, 317, 927, 2007 and U.S. Pat. No. 8,003,965. Such highly oscillatory evanescent fields are realized using near-field plates (NFPs). NFPs are non-periodically patterned surfaces, which are designed to form a prescribed subwavelength focal pattern at a specified focal plane. NFPs have demonstrated several advantages over metamaterial superlenses. Firstly, NFPs are patterned surfaces or arrays which are much simpler to fabricate compared to volumetric metamaterial superlenses. Secondly, NFPs have been shown to be robust to practical losses. Thirdly, NFPs allow one to stipulate the subwavelength near-field focal pattern, a unique feature not offered by metamaterial superlenses. Fourthly, the design of NFPs is scalable with frequency. For example, NFPs have been pursued from kilohertz to optical frequencies.

While previous NFPs have demonstrated extreme field tailoring capability to form subwavelength focal patterns, their performance was limited by undesired fields in directions other than the direction of the subwavelength focus or field maximum. This issue can limit the utility of NFPs in practical applications. For example, an NFP which is used as a probe to detect objects in its focal plane may couple to objects in locations other than the focal plane. Thus, it is desirable to have an NFP that concentrates radiation from a source into subwavelength dimensions without reflection. In other words, the NFP should form a “unidirectional” subwavelength near-field pattern.

SUMMARY

The present techniques allow for the design of an NFP that can form a unidirectional subwavelength near-field pattern. Specifically, the NFP forms a prescribed subwavelength focal pattern with significantly reduced electromagnetic field in directions other than the desired focal pattern. As a result, the NFP proposed here overcomes numerous obstacles for incorporating the use of NFPs in practical applications.

In an example, a method for unidirectional subwavelength focusing and near-field manipulation using near-field plates comprises: generating a source field pattern from an excitation source at a focal plane; generating a subwavelength field pattern from a near-field plate when the near-field plate is excited by the excitation source, the near-field plate being at a distance, d, from the excitation source; forming a desired field pattern at the focal plane from the subwavelength field pattern and the source field pattern, the focal plane being at a distance, L, from the excitation source; and configuring the desired field pattern to be a unidirectional subwavelength field pattern in a desired direction by increasing the amplitude of the desired field pattern in the desired direction.

In another example, an apparatus for unidirectional subwavelength near-field focusing comprises: an excitation source generating a source field pattern and a near-field plate generating a subwavelength field pattern when excited by the excitation source; where after traversing a near-field distance, L, the source field pattern and the subwavelength field pattern form a desired field pattern at a focal plane, and where the desired field pattern is a unidirectional subwavelength field pattern when the amplitude of the subwavelength field pattern is increased.

In accordance with another example, a method for wireless transfer of power from a transmitting side to a receiving side, the method comprises: generating a source field pattern energy from an excitation power source at a focal plane of the transmitting side; generating a subwavelength field pattern of energy from a transmitting side near-field plate when the near-field plate is excited by the excitation source, the transmitter side near-field plate being at a distance, d, from the excitation source; receiving energy at the receiving side in a desired field pattern received by a receiving side near-field plate positioned to excite a power receiver, where the desired field pattern is formed at a focal plane of the receiving side and from the subwavelength field pattern and the source field pattern, the focal plane of the receiving side being at a distance, L, from the excitation source, and wherein the receiving side near-field plate is positioned at the focal plane of the receiving side; and converting the received energy into a received power, at a power conversion efficiency.

In accordance with another example, an apparatus for wireless power transfer from a transmitting side to a receiving side, the apparatus comprises: an excitation power source generating a source field pattern energy at the transmitting side; a transmitting side near-field plate generating a subwavelength field pattern energy when excited by the excitation source, wherein after traversing a near-field distance, L, the source field pattern energy and the subwavelength field pattern energy form a desired field pattern energy at a focal plane, wherein the desired field pattern energy has a unidirectional subwavelength field pattern when the amplitude of the subwavelength field pattern is increased; and a power receiver and a receiving side near-field plate at the receiving side, the receiving side near-field plate being positioned at the focal plane and spaced a distance from the power receiver to couple a received energy from desired field pattern energy to the power receiver, wherein the power receiver is configured to convert the received energy into a received power for provision to a load.

BRIEF DESCRIPTION OF THE DRAWINGS

For a more complete understanding of the disclosure, reference should be made to the following detailed description and accompanying drawing figures, in which like reference numerals identify like elements in the figures, and in which:

FIG. 1 illustrates an example NFP configuration that includes non-periodically modulated surface impedance strips;

FIG. 2 illustrates focal patterns produced by NFPs with various amplification factors;

FIGS. 3A-3C illustrate two-dimensional contours of near-field patterns formed by NFPs with various amplification factors;

FIGS. 4A and 4B illustrate plots of the near-field patterns produced by NFPs with various amplification factors on a circle centered at the origin;

FIGS. 5A-5F illustrate plots of the signals detected by the simulation of a coaxial probe with and without NFPs as metallic cylinders are moved along the focal plane;

FIGS. 6A and 6B illustrate configurations used in the simulation of a coaxial probe with NFPs as metallic cylinders are moved along the focal plane; and

FIG. 7 illustrates a wireless power transfer system using unidirectional NFPs.

FIG. 8 illustrates a wireless power transfer system using NFPs on each of the transmitter side and receiver side.

FIG. 9 illustrates an example of a transmitter side NFP (left) and a receiver side NFP (right) as may be used in the configurations of FIGS. 7 and 8, in an example.

FIGS. 10A-10C are plots for different near-field plate configurations showing a comparison of power transfer efficiency.

FIGS. 11A and 11B are plots illustrating power transfer efficiency improvements from transmitter side and receiver side NFPs compared to other configurations.

While the disclosed methods and apparatus are susceptible to embodiments in various forms, there are illustrated in the drawing (and will hereafter be described) specific embodiments of the invention, with the understanding that the disclosure is intended to be illustrative, and is not intended to limit the invention to the specific embodiments described and illustrated herein.

DETAILED DESCRIPTION

Near-field plates or NFPs are used to generate extreme electromagnetic confinement. Typically, NFPs are designed to form a prescribed subwavelength electromagnetic focal pattern when excited by a specific source. However, previous NFP designs exhibit pronounced field in undesired directions (e.g., back radiation), thereby limiting their utility in practice. The present techniques allow for the design of an NFP with a unidirectional subwavelength near-field pattern. Unidirectionality is achieved via adjustment of the field amplitude at the focal plane of the NFP. To produce a larger field amplitude at the focal plane (forward direction), the electromagnetic field radiated by the NFP needs to interfere constructively with the field radiated from the source in the desired forward direction, but destructively in other unwanted directions. This phenomenon can be better explained by considering the NFP as current elements with an overall current that is equal to the sum of the currents induced on the NFP. Thus, if the overall current of the NFP has a negative phase and a magnitude close to the current from the source, then a desired unidirectional pattern can be formed.

Generally speaking, NFPs may be in the form of planar structures that focus electromagnetic radiation to spots or lines. These planar structures act as impedance sheets possessing a non-periodically modulated surface impedance (capacitive or inductive reactance), where the modulated surface impedance sets up a highly oscillatory electromagnetic field that converges at the focal plane of the planar structures. The NFPs may be directly excited or illuminated or excited by elementary electromagnetic sources such as plane waves, cylindrical sources, finite sources, etc.

FIG. 1 illustrates an example NFP configuration which can be used to form a unidirectional subwavelength near-field pattern. As shown in the embodiment of FIG. 1, the NFP configuration includes a plate with 2N+1 elements each having a width w and a surface impedance Z_(n), where n=−N . . . +N. In this manner, the example NFP of FIG. 1 comprises a plurality of non-periodically modulated surface impedance elements. In an embodiment, subwavelength metallic or dielectric patterning may be used to realize the plurality of non-periodically surface impedance elements.

In some embodiments, the NFP configuration may include shapes other than the rectangular elements shown in FIG. 1. For example, the NFP configuration may include elements of various shapes and sizes, including but not limited to circular shaped elements, circular ring shaped elements, arc-shaped elements, U-shaped elements, elliptical shaped elements, elliptical ring shaped elements, L-shaped elements, T-shaped elements, cross-shaped elements, trapezoidal shaped elements, anisotropic elements, etc. Moreover, the elements of the different NFP configurations may be arranged in a regular or irregular lattice, for example.

In FIG. 1, the example near-field plate is located at x=d and is excited by a line source at the origin with a current of I. Both the plate and the line source are assumed to be infinite in the z direction. To form the unidirectional subwavelength near-field pattern, the impedances Z_(n) of the plate must be determined such that the plate and line source form a desired subwavelength focus, E_(z) ^(focal), at x=L. An example of a desired focal pattern may be:

E _(z) ^(focal)(y _(n))=jM|E _(inc)(x=L, y=0)|f(y _(n))  (1)

where M is an amplification factor, |(x=L, y=0)| is the maximum of the field incident from the line source at the focal plane, and f (y_(n)) is the desired subwavelength pattern. The pattern is multiplied by a complex number (in this case the imaginary number j) to ensure that the impedance elements are predominantly reactive.

The goal of the design procedure is to find the impedances Z_(n) of an NFP that form a prescribed focal pattern E_(z) ^(focal). To accomplish this, the current densities K_(n) on the surface of the plate that generate the desired focal pattern E_(z) ^(focal) needs to be determined. The current densities K_(n) can be related to E_(z) ^(focal) by an electric field integral equation, which can be discretized and represented by the following matrix equation:

$\begin{matrix} {{{\frac{- {kZ}_{0\;}}{4}{\sum\limits_{m = {- N}}^{N}{K_{m}{{wH}_{0}^{2}\left( {k\; \rho_{mn}} \right)}}}} + {E_{inc}\left( {{x = L},y_{n}} \right)}} = {E_{z}^{focal}\left( y_{n} \right)}} & (2) \end{matrix}$

where k is the free space wavenumber, Z₀=120π is the free space impedance, H₀ ² is the zero-order Hankel function of the second kind, and E_(inc)(x=L, y_(n)) is the incident field from the line source at the focal plane, sampled at y_(n)=nw. In Equation (2), the width of the surface impedance elements w is assumed to be electrically small. Therefore, the field radiated by each element can be approximated by a line source with current K_(m) ^(w) located at y_(m)=mw and at a distance ρ_(mn)=√{square root over ((y_(n)−y_(m))²+(L−d)²)}{square root over ((y_(n)−y_(m))²+(L−d)²)} from the observation point y_(n). The incident electric field E_(inc) due to the source can be computed using following equation:

$\begin{matrix} {{E_{inc}\left( {x,y} \right)} = {\frac{- {kZ}_{0}}{4}{{IH}_{0}^{2}\left( {k\sqrt{x^{2} + y^{2\;}}} \right)}}} & (3) \end{matrix}$

where I is the amplitude of the line current source. Equation (2) can now be solved to find the required current densities K_(n). Once K_(n) are known, they can be used to find the field at the surface of the plate. The ratios of the fields at the surface of the plate to the current densities are then taken to find the required impedances Z_(n).

Equation (1) allows one to design an NFP by stipulating both the spatial distribution of the focal pattern through f(y) and the amplitude of the focal pattern through M. Earlier works primarily focused on forming subwavelength focal patterns with various spatial distributions by modifying f(y). As such, NFPs have been designed to generate a subwavelength sinc function as discussed by A. Grbic, L. Jiang, and R. Merlin, Science, 320, 511, 2008, an Airy pattern as discussed by M. F. Imani and A. Grbic, Appl. Phys. Lett., 95, 111107, 2009, and Bessel focal patterns as discussed by M. F. Imani and A. Grbic, IEEE Trans. Antennas and Propag., 60, 3155, 2012. While these works confirmed the field tailoring capabilities of NFPs, they did not explicitly explore adjusting the amplitude of the generated focal patterns.

The present techniques focus on manipulating the near-field by varying the amplification factor, M. The amplification factor can be chosen carefully such that the NFP interferes constructively with the field due to the line source in the forward direction and destructively in other directions. The mechanism behind creating unidirectional field patterns can be understood by considering antenna array theory, in which the NFP is approximated as a line source with overall current I_(NFP) that is equal to the sum of the currents induced on the NFP. Based on antenna array theory, the phase of I_(NFP) should be negative and its magnitude should be close to |I| in order to form a unidirectional pattern. To achieve these conditions, the currents on the NFP relative to that of the source are adjusted by varying M.

The two element antenna array discussed above resembles, for example, the end-fire superdirective arrays discussed by A. D. Yaghjian, T. H. O'Donnell, E. E. Altshuler, and S. R. Best, Radio Science, 43, 2008, or the unidirectional ultracompact optical antennas discussed by T. Pakizeh and M. Kall, Nano Letters, 9, 2343, 2009. However, the objective of these earlier works is to form a superdirective far-field pattern while the goal here is to form a unidirectional subwavelength focus in the near-field.

In order to demonstrate how the near-field formed by the NFP can be controlled by changing M, three example NFPs are designed and studied with different values of M. The plates of each of the designed NFPs comprise 5 elements. Each plate is designed to operate at f=1 GHz (λ=300 mm) The width of the elements is selected to be w=15 mm=λ/20, which results in plates that are λ/4 wide. The plates are located at d=10 mm=λ/30 and the focal plane is at L=20 mm=λ/15. The amplitude of the line source with current I is arbitrarily set to 1 A. The subwavelength focal pattern is selected to be a Bessel pattern truncated by a Gaussian function such that:

f(y _(n))=exp(−y _(n) ²/2σ²)J ₀(qy _(n))  (4)

where σ=19 mm determines the full-width at half-maximum (FWHM) of the Gaussian truncation, J₀ is the zeroth order Bessel function, and q=3 k determines the beamwidth of the Bessel function. The plates are designed for amplification factors of M=0.3, M=1.2, and M=2.1. The corresponding surface impedances are listed below in Table 1.

TABLE 1 index M = 0.3 M = 1.2 M = 2.1 0 0.73-20.66j 0.29-40.80j −0.05-46.59j 1 2.88-31.76j −1.40-116.86j −15.36-180.20j 2 −7.98-28.92j  −2.01-19.49j  −1.88-18.54j

The designed NFPs are simulated using a commercial electromagnetic solver. For the purpose of simulation, the designed NFPs and the corresponding line sources are placed between two horizontal metallic plates of a parallel plate waveguide which are at z=0 and z=H=15 mm planes. According to image theory, the metallic plates of the waveguide accurately model the structure shown in FIG. 1, which is infinite and invariant in the z direction. The real parts of the surface impedances listed in Table 1 are neglected and their reactive parts are realized using capacitances computed using

${C_{n} = \frac{1}{\omega \; {H/W}\; {{Imag}\left( Z_{n} \right)}}},$

as discussed by A. Grbic, L. Jiang, and R. Merlin, Science, 320, 511, 2008, where w is the angular frequency. In practice, such capacitive surface impedances can be realized using interdigitated capacitors at microwave frequencies as discussed by A. Grbic, L. Jiang, and R. Merlin, Science, 320, 511, 2008, or dielectric nanocircuit elements as discussed by N. Engheta, A. Salandrino, and A. Alù, Phys. Rev. Lett., 95, 095504, 2005 at optical frequencies. For simulation purposes, the surface impedance boundaries are used because interdigitated capacitors are computationally intensive to simulate. The surface impedances are assumed to be lossy with a conservative quality factor of Q=100.

The simulated focal patterns for the designed NFPs, for some examples, are shown in FIG. 2. For comparison purposes, the pattern due to the line source alone is also depicted. The designed NFPs produce focal patterns with much narrower beamwidth when compared to the line source alone. Specifically, the FWHM of the focal pattern produced by the designed NFPs is 0.125λ, whereas that of the line source alone is 5 times wider at 0.623κ. While the three designed NFPs produce focal patterns with similar subwavelength beamwidths, their field amplitude is different due to the different amplification factors. To further highlight the ability of the NFP to concentrate the electromagnetic field, the pattern due to the line source when it is moved to the location of the NFP (x=d) is also depicted in FIG. 2. The beamwidth of this pattern is still wider than that of NFPs. Specifically, its FWHM is 0.361κ, which is 2.89 times wider than that of the NFPs.

FIG. 3 (FIGS. 3A-3C) illustrates the evolution of the near-field patterns formed by the three designed NFPs as the amplification factor, M, is increased. FIG. 3 plots the two-dimensional contours of the simulated |E_(z)| patterns formed by the three NFPs. In FIG. 3A, the near-field pattern formed by the NFP with an M=0.3 is shown. This NFP exhibits pronounced reflection similar to earlier NFP designs discussed by M. F. Imani and A. Grbic, Metamaterials, 4, 104, 2010.

As the amplification factor is increased, more field is directed in the x>0 direction while the field emitted in other directions is reduced. This can be seen in FIG. 3B and FIG. 3C, where the unidirectional near-field patterns for the NFPs with M=1.2 and M=2.1 are shown, respectively. This phenomenon is in fact similar to that observed in Yagi-Uda antennas, where the far-field radiation is unidirectional. In Yagi-Uda antennas, a parasitic element directs the radiation emitted by an elementary antenna to form a unidirectional far-field pattern. In a similar fashion, an NFP acts as a director element to form a unidirectional subwavelength (directive) near-field pattern.

The variations in the near-field patterns formed by the NFPs in FIG. 3 can also be explained by examining the overall current, I_(NFP), induced on the NFP for different amplification factors, M, as listed in Table 2.

TABLE 2 M = 0.3 M = 1.2 M = 2.1 I_(NFP) 0.96 < 176 0.99 < −169 1.06 < −156

As mentioned earlier, a negative phase of I_(NFP) (a phase lagging the excitation source) results in a unidirectional pattern. In Table 2, the phase of I_(NFP) is positive for M=0.3, which corresponds to the pronounced reflection seen in FIG. 3A. As M is increased, the phase of I_(NFP) changes. In fact, it can be shown that the phase flips around M=0.55. Above this value of M, the phase of I_(NFP) is negative (see Table 2) and a unidirectional pattern is formed as can be seen in FIG. 3B and FIG. 3C.

FIG. 4A illustrates the simulated |E_(z)| patterns formed by the three NFPs as plotted on a circle of radius 75 mm=κ/4 centered at the origin. As M is increased from 0.3 to 1.2, the field amplitude at θ=0 increases while the field amplitude in other directions is suppressed. By further increasing M from 1.2 to 2.1, the field amplitude in all directions increases. However, this increase is not uniform for all directions. For example, the ratio of the field amplitude in the forward direction (θ=0) over the backward direction (θ=180) is 5.2 for M=1.2. It reduces to 2.55 for M=2.1. Therefore, any further increase in M does not necessarily improve the unidirectionality of the formed near-field pattern.

To further illustrate how I_(NFP) listed in Table 2 can be used to explain the near-field pattern formed by the three NFPs, the |E_(z)| patterns formed by the three I_(NFP) listed in Table 2 and the current source have also been computed (on the same circle as FIG. 4A). The results are shown in FIG. 4B. As one can see, the pattern formed by I_(NFP) corresponding to M=0.3 exhibits significant reflections. However, the other two current values corresponding to M=1.2 and M=2.1 predict unidirectional patterns. The similarity between the predictions of FIG. 4B and FIG. 4A clearly demonstrate how I_(NFP) can be used to explain the formation of the unidirectional near-field. It should be noted I_(NFP) is an approximation of the currents formed on the NFP and the small differences between the FIG. 4A and FIG. 4B are expected.

A closer look at the impedance values in Table 1 reveals another aspect. As M is increased, the real part of the impedance elements becomes negative. Negative real impedance indicates gain which cannot be realized using passive elements. This trend is in fact expected since increasing the amplification factor requires larger field amplitude at the focal plane. When the field amplitude becomes too large (e.g., when M=10), it can only be achieved by using active elements that amplify the field since passive resonant amplification is limited due to losses. Therefore, large amplification factors of M are not physically possible using solely passive elements. However, when the negative real part of the impedances are negligible compared to their imaginary part (as it is the case for M=2.1), the designed NFPs can be approximated using passive reactive impedances.

The unidirectional subwavelength focus created by the designed NFPs may find numerous applications. In particular, it can be used to increase the sensitivity and resolution of imaging and probing instruments. To demonstrate the potential of the designed NFPs as highly sensitive probes with subwavelength resolutions, the designed NFPs are simulated with the line source replaced with a coaxial probe. The designed NFPs and the corresponding coaxial probes are placed between two horizontal metallic plates of a parallel plate waveguide which are at z=0 and z=H=15 mm planes. The inner and outer conductors of the coaxial probe are connected to the upper and lower plates of the parallel plate waveguide. The inner and outer radii of the probe are 0.635 mm and 2.05 mm, respectively. With this arrangement, an NFP can confine the near-field of the coaxial probe to a unidirectional subwavelength focal pattern. As a result, any object placed at the focal plane significantly alters the near-field formed by the NFP. This change can be detected by examining the reflection coefficient of the coaxial probe.

To verify this proposition, the designed NFPs listed in Table 1 are simulated when a metallic cylinder of radius 0.635 mm=0.002λ is placed along their focal plane (see FIG. 6A for simulation configuration). The metallic cylinder is moved along the focal plane and the reflection coefficient, Γ^(cyl) is recorded. The reflection coefficient without the metallic cylinder, Γ⁰ is also recorded. The change in reflection coefficient is then enhanced by computing the expression (Γ^(cyl)−Γ⁰)/(1−Γ^(cyl)Γ⁰) as shown by L. Markley and G. Eleftheriades, J. Appl. Phys., 107, 093102, 2010. Signals detected in this manner are shown in FIG. 5.

FIG. 5A plots the signal detected by the coaxial probe alone and in the presence of the designed NFPs listed in Table 1. The signal detected by the coaxial probe alone when it is moved to the location of the NFP (x=d) is also depicted. The results show that using a unidirectional NFP allows detection of the subwavelength metallic cylinder, while the coaxial probe can barely detect the metallic cylinder, even when it is moved to the location of the NFP. FIG. 5A also reveals that increasing the amplification factor, M, increases the sensitivity of the near-field probe. This can be expected because a larger amplification factor results in a larger field amplitude at the focal plane. The metallic cylinder causes a larger perturbation in a larger field amplitude, and thus leads to a higher sensitivity.

To examine the resolution of the probe based on the unidirectional NFP, two identical metallic cylinders (with radius of 0.635 mm), separated by a distance s, are placed along the focal plane (see FIG. 6B for simulation configuration). Here, only the NFP with M=2.1, which exhibits the highest sensitivity in FIG. 5A, is studied. The two cylinders are moved along the focal plane and the changes in the reflection coefficient are recorded. The signal detected in this manner for various distances s are plotted in FIG. 5B to FIG. 5E, which clearly illustrates the capability of the unidirectional NFP in resolving two subwavelength cylinders which are subwavelength distance apart. Without the unidirectional NFP, the coaxial probe barely distinguishes between the two metallic cylinders, even though the probe has been moved to the location of the NFP. The unidirectional NFP probe described above holds promise for high resolution, highly sensitive probing.

In addition to applications in imaging and probing systems, the designed NFPs may find application in biomedical devices, where the unidirectional subwavelength focus created by the NFPs can be used to develop accurate targeting and stimulating devices. In high density data storage, the designed NFPs can be advantageous in increasing the density of data storage due to their confined focus with suppressed field in other directions. In wireless power transfer systems, the designed NFPs can be used to maintain power transmission to a receiver without radiating in unwanted directions. This can significantly reduce power leakage, interference, and health concerns.

More particularly, in an application involving wireless power transfer, a unidirectional NFP can be placed close to the transmitting loop of a wireless power transfer system to yield a unidirectional wireless power transfer transmitter. In doing so, the unidirectional NFP can significantly reduce the radiation due to the transmitting loop into unwanted directions. This is different from current wireless power transfer systems where a ferrite slab is usually used to reduce the power transmission into unwanted directions. Ferrites are heavy, expensive, lossy and are not eco-friendly to produce. On the other hand, the unidirectional NFP is straightforward to fabricate and low cost, and can form unidirectional near-field patterns with minimal loss. Moreover, these advantages can occur in a single, unitary structural design without the need for additional radiation blocking elements. Further, because the unidirectional NFP and the transmitting loop are out of phase, their combined far-field radiation is much smaller than the field due to the transmitting loop alone. Still further, the unidirectional NFP can form a unidirectional near-field pattern with minimal effect on the efficiency of the wireless power transfer system.

FIG. 7 illustrates an example wireless power transfer system 700 that uses a unidirectional NFP. The example wireless power transfer system 700 includes a charger 702 and a device 704 to be charged (e.g., a computer, a smartphone, a biometric sensor device, a chargeable battery, an automobile or other vehicle using a chargeable battery, consumer electronics, implanted medical devices, etc.). The charger 702 includes a transmitting loop 706 and a unidirectional NFP 708. The unidirectional NFP 708 can control the radiation pattern emitted by the transmitting loop 706. For example, the magnetic field pattern in a desired upward direction (e.g., the normal direction) is enhanced, while the magnetic field radiation pattern in other unwanted directions (e.g., lateral directions) is reduced. Thus, by connecting the device 704 to a receiving loop 710, power can be efficiently transferred to the device 704 without the magnetic field interfering with other electronic devices, or causing health concerns in unwanted directions.

In the embodiment of FIG. 7, the transmitting loop 706, the unidirectional NFP 708 and the receiving loop 710 are all circular. However, in other embodiments, other shapes may be used (including in array form), such as ellipses, squares, triangles, and irregular and asymmetrical shapes. While the axes of the loops are shown to be perpendicular to the NFP in FIG. 7, in other embodiments, the axes of the constituent loops may be arranged perpendicularly and/or in-plane with respect to the surface of the NFP. The transmitting loop 706, the unidirectional NFP 708 and the receiving loop 710 may be made out of copper or other suitable conductive material.

The unidirectional NFP 708 is configured to comprise an array of loops, each of which is loaded with a designed impedance to form a desired unidirectional near-field. There are several factors that affect the choice for the number of loops in the NFP loop array 708. From a design point of view, a higher number of loops may be desired because increasing the number of loops increases the range of the near-field patterns that can be produced (more degrees of freedom). However, considering the wireless power transfer application, it may be desirable to keep losses as low as possible. Thus a trade-off may be evaluated because introducing a new loop may in fact increase the losses due to the added ohmic loss in the copper. In the embodiment of FIG. 7, the NFP loop array 708 is shown to include a large central loaded loop in addition to four identical smaller loops, which have identical loading impedances. The four smaller loops in the NFP loop array 708 are uniformly placed to keep the produced near-field pattern symmetric. It should be noted, however, that this is not the only configuration possible for the unidirectional NFP 708. In other embodiments or scenarios, a higher number of loops in the NFP loop array 708 may be more practical.

Further, the radius of the large central loaded loop is selected to be similar to the transmitting loop 706. The radiuses of the four smaller loops are selected to fit inside the central loaded loop in order to maintain high mutual coupling. In other embodiments or scenarios, the radiuses of the smaller loops may be chosen to be smaller or bigger. Importantly, the loading impedances of the NFP loop array 708 may be designed such that the required currents are induced on the NFP loop array 708 to form the desired unidirectional near-field pattern. The loading impedances may be realized by using lumped element impedances or distributed impedances (e.g., transmission lines).

As shown in FIG. 7, the unidirectional NFP 708 is placed at the top portion of charger 702 while the transmitting loop 706 is situated at the bottom portion of the charger 702. The distance between the transmitting loop 706 and the unidirectional NFP 708 is used to obtain the necessary asymmetry to produce the desired unidirectional field pattern. As discussed earlier, the current on the transmitting loop 706 and the unidirectional NFP 708 should be out of phase in order to form the unidirectional field pattern. If the transmitting loop 706 and the unidirectional NFP 708 are too close to one another or on the same plane, then they would (almost) cancel each other's fields. Accordingly, the field received at the receiving loop 710 would be very low, resulting in low power transfer efficiency. By increasing the distance between the transmitting loop 706 and the unidirectional NFP 708, the field received at the receiving loop 710 can increase and thus result in high power transfer efficiency. This is in fact an advantage of using a unidirectional NFP for wireless power transfer applications. The unidirectional NFP can be used to form a high amplitude and highly confined electromagnetic field in the near-field, while reducing the field in unwanted directions as well as in the far-field. In wireless power transfer systems, high amplitude electromagnetic fields that are formed in unwanted directions (i.e., power leakage) can cause health concerns, interfere with other electronic devices, or hinder metering. The unidirectional NFP 708 significantly mitigates power leakage, while maintaining high power transfer efficiency. Of course, it should be noted that for practical considerations, the distance between the transmitting loop 706 and the unidirectional NFP 708 should be small so as to reduce the overall dimension of the charger 702.

In an embodiment, the wireless power transfer system 700 may be used to charge any suitable computing device such as a laptop computer, a smartphone, a personal digital assistant, a tablet computer, etc. In another embodiment, the wireless power transfer system 700 may be used to charge various biometric sensor devices such as a fingerprint sensor, a heart rate sensor, ventricular assist device, implantable wireless device, an iris scanner, etc. In yet another embodiment, the wireless power transfer system 700 may be used to charge any type of chargeable or rechargeable battery. In still another embodiment, the wireless power transfer system 700 may be used to charge any device or piece of equipment that uses a chargeable or rechargeable battery such as an electric car, an electric motorcycle, an electric bus, an electric boat, etc.

Overall, compared to many competing technologies, such as metamaterial superlenses, the unidirectional NFPs disclosed herein are superior due to their unidirectionality, support for the stipulation of the subwavelength near-field pattern, simplified fabrication, and improved performance.

In other examples, magnetic near-field plates as provided herein may be used on both the transmitting side and the receiving side of a wireless power transfer system. For example, the near-field plates described herein may be used on a transmitting loop, as described, and also on a receiving loop, where the addition of the receiver side near-field plate has been shown to particularly improve power transfer efficiency and provide magnetic field tailoring.

FIG. 8 illustrates an example wireless power transfer system 800 that uses NFP's on each of a transmitter side 802 and a receiver side 804. The transmitter side 802 includes a transmitter loop 806 that transmits an RF power wirelessly to a receiver loop 808 that is part of the receiver side 804. The transmitter loop 806 receives an input voltage signal from a power source 810 (e.g., a voltage source, V_(S)) coupled to the loop 806 through an impedance matching circuit 812. A characteristic resistance 811 (R_(S)) is also depicted representing the impedance of the power source 810. Correspondingly, the receiver 804 includes an impedance matching network 814 connected between a resistance load 816 (R_(L)) and the receiver loop 808, where the load 816 represents a circuit or other element connected to the receiver loop 808, for example, to process a received power signal.

The transmitter side 802 includes the transmitter loop 806 and a transmitter NFP 820, where the two may have fixed positions relative to each other. The transmitter loop 802 is an electrically conducting loop that is electrically connected to the power source and carries an alternating current, which produces a magnetic field.

The receiver side 804 includes the receiver side NFP 822, which may be the same or different than the transmitter loop 820.

FIG. 9 illustrates an example of the transmitter NFP 820 formed of a series of loops 824 in a concentric configuration. Each of the loops 824 are able to carry current due to inductive coupling from the magnetic field produced by the transmitter loop 802. The loops 824 are defined by their centroid points, which are all the same in the illustrated example. The loops 824 are also defined by an average radius for each loop, i.e., a radius centered between an inner radius and an outer radius. Further still, the loops 824 are defined by a radial thickness, which is the same for each of the loops 824. Any of these variables can be adjusted to tune the operation of the transmitter NFP 820, in terms of directionality but also coupling efficiency to the transmitter loop 806.

In an example implementation, the contiguous loop of each loop 824 is broken by one or more gaps 825, across which are placed reactive (capacitive and/or inductive) elements (not shown). The gaps 825 may be radial aligned as shown, or one or more of them may be offset from the other. The value of the reactive elements determines the induced current in each loop 824, and as such the reactance of the reactive elements can be adjusted to determine the desired induced current. Such adjustment can be made based on the gap size and/or the reactance value of the element. The total magnetic field produced by the transmitter 802 is a function of the currents in the transmitter loop 806 and the NFP 820. The reactive elements in the NFP 820 may be chosen using an optimization algorithm to produce a magnetic field with the desired properties.

The receiver loop 808 is an electrically conducting loop that is electrically connected to the load 816 and carries an induced alternating current due to the magnetic field produced by the transmitter side 802 and the receiver NFP 822.

The receiver NFP 822 may be symmetric with the transmitter NFP 820, meaning the two have the same shape configuration or generally have the same shape configuration. In the illustrated example, that shape configuration is concentric rings. In the illustrated example, a plurality of loops 826 are shown in a concentric configuration. Similarly, the loops 826 carry currents due to magnetic induction.

Each loop 826 may be broken by one or more gaps 827, across which are placed reactive elements, in a similar way to the transmitter NFP 820. Similarly, the value of the reactive elements determines the induced current in each loop, and may likewise be determined using an optimization algorithm.

The system 800 operates in the electromagnetic near field. That is, all structures (e.g., loops 822 and 826) are electrically small compared to the wavelength λ=c/f, and the working distance between the transmitter side 802 and receiver side 804 is also small compared to the wavelength, as are the distances between the transmitter loop 806 and the transmitter NFP 820 and the receiver loop 80 and the receiver NFP 822.

For a given choice of capacitive elements in the NFP loops and given relative position of transmitter and receiver units, the maximum power transfer occurs when the input to the transmitter loop 804 and output of the receiver loop 808 are simultaneously impedance matched. That is, _(Zs)=_(Z) ^(*) _(in) and _(ZL)=_(Z) ^(*) _(out). The impedance matching circuits 812 and 814 are designed to achieve this over the operating frequencies of the system 800. In some examples, these impedance matching circuits 812 and 814 may be actively controlled.

By using a NFP on both the transmitter and receiver side of a power transfer system, we were able to improve maximum power transfer efficiency, in addition to directionality on the magnetic fields during power transfer. The reactive elements, the type of NFPs, the configuration of the loop elements in the NFPs, the size of the loops in the NFPs, the symmetry of the transmitter NFP and the receiver NFP can all be adjusted using an optimization algorithm to achieve the desired performance.

FIGS. 10A-10C illustrate power transfer efficiency improvement in an example simulation, showing results for different near-field plate configurations. In this example, the transmitter and receiver loops were single loops with printed copper traces with 8 cm outer diameters. The present techniques may be used with any number of transmitter and receiver loop configurations, including for example, multiple-turn coils used in wireless power transfer, e.g., those used in conjunction with the Wireless Power Consortium (WPC) and Alliance for Wireless Power (A4WP) group.

The transmitter and the receiver near-field plates each contained four concentric printed loops and were each in plane spaced 0.5 cm apart from the transmit loop and receive loop, respectively. The operating frequency of the system, i.e., on the transmitter and receiver sides, was 6.78 MHz ISM band. FIGS. 10A-10C show the three configurations that are compared, namely single-loop transmitter and receiver with no NFPs (FIG. 10A), an NFP on the transmitter only (FIG. 10B), and finally NFPs on both the transmitter and receiver (FIG. 10C). FIGS. 10A-10C also show the coordinates used in the efficiency comparison: the air gap L between transmitter and receiver units, and the separation a between the transmitter and receiver central axes.

The maximum power transfer efficiency (assuming ideal impedance matching) was calculated for a variety of distances of the airgap, L, between the transmitter and receiver, as well as for various lateral offsets at a distance of 8 cm. The efficiency was measured using the following expression:

$\eta_{RF} = \frac{P_{L}}{P_{AVS}}$

where P_(L)=1/2|i_(L)|²R_(L) is the power delivered to the load, and P_(AVS)=|V_(s)|²/8 R_(s) is the maximum power available from the source. It can be shown that the power delivered across the loops is maximized when conjugate impedance matching is simultaneously achieved at both the input and output. That is, when _(Zs)=_(Z) ^(*) _(in) and _(ZL) 32 _(Z) ^(*) _(out).

As shown in FIGS. 11A and 11B, using a NFP with both the transmitter and receiver allowed for a significant efficiency improvement compared to the other configurations. FIG. 11A illustrates the efficiency as a function of the airgap spacing, L, for an operating frequency of 6.78 MHz when the transmitter unit and receiver unit axes are aligned (a=0). FIG. 11B illustrates the efficiency as a function of the lateral offset a between the transmitter unit and receiver unit central axes at a constant air gap L. Such optimization can be combined with NFP configurations, like discussed herein, that are designed to reduce the magnetic filed in unwanted directions, such as suppressing the magnetic field in the direction opposite power transfer. The pairing of two NFP plates also means that a larger magnetic field may be maintained between the transmitter loop and the receiver loop, for larger power transfer, while at the same time, the magnetic field beyond the transmitter and receiver may be suppressed. In this way, the dual NFP configuration can be used to provide much faster power transfer and much faster device charging times, for example, without exposing the environment surrounding the charging device to considerably greater amounts of magnetic field. The dual NFP configuration also allows for a greater operating range. The example system operated at 6.78 MHz, but typical operating frequencies will range from about 100 kHz to over 40 MHz.

FIG. 9 illustrates example near-field plates using concentric loops, but other configurations can be used, by adjusting the number, size, and placement of loops forming the NFP. Any of the NFPs described herein may be used, for example. Moreover, in some examples, the NFPs can be placed in the same plane as the associated transmitter or receive loop, rather than offset as shown in the example. Moreover still, the NFP loops can be oriented at an angle relative to the associated transmit or receive loop, rather than parallel as shown in the example. Moreover still, the power coupling efficiency and the configuration of NFP elements and features will also vary with the type of transmitting and receiving loop.

While the present invention has been described with reference to specific examples, which are intended to be illustrative only and not to be limiting of the invention, it will be apparent to those of ordinary skill in the art that changes, additions and/or deletions may be made to the disclosed embodiments without departing from the spirit and scope of the invention.

The foregoing description is given for clearness of understanding; and no unnecessary limitations should be understood therefrom, as modifications within the scope of the invention may be apparent to those having ordinary skill in the art. 

What is claimed:
 1. A method for wireless transfer of power from a transmitting side to a receiving side, the method comprising: generating a source field pattern energy from an excitation power source at a focal plane of the transmitting side; generating a subwavelength field pattern of energy from a transmitting side near-field plate when the near-field plate is excited by the excitation source, the transmitter side near-field plate being at a distance, d, from the excitation source; receiving energy at the receiving side in a desired field pattern received by a receiving side near-field plate positioned to excite a power receiver, where the desired field pattern is formed at a focal plane of the receiving side and from the subwavelength field pattern and the source field pattern, the focal plane of the receiving side being at a distance, L, from the excitation source, and wherein the receiving side near-field plate is positioned at the focal plane of the receiving side; and converting the received energy into a received power, at a power conversion efficiency.
 2. The method of claim 1, further comprising: increasing the amplitude of the desired field pattern by varying an amplification factor at the transmitting side.
 3. The method of claim 1, further comprising: increasing the power conversion efficiency at the receiving side by varying a distance between the receiving side near-field plate the power receiver.
 4. The method of claim 1, wherein the excitation power source is a transmitting loop and wherein the power receiver is a receiving loop.
 5. The method of claim 4, wherein the transmitting side near-field plate has the same configuration as the receiving side near field plate.
 6. The method of claim 4, wherein the transmitting side near-field plate has a different configuration than the receiving side near field plate.
 7. The method of claim 4, wherein the transmitting side near-field plate is formed of a plurality of concentric loops.
 8. The method of claim 4, wherein the receiving side near-field plate is formed of a plurality of concentric loops.
 9. The method of claim 4, wherein the transmitting loop comprises a multi-turn coil; and the receiving loop comprises a multi-turn coil.
 10. The method of claim 1, further comprising: supplying the received power to a device for wirelessly power the device or wirelessly charging the device, wherein the device includes one or more of a computer, a smartphone, a biometric sensor device, a chargeable battery, or a vehicle using a chargeable battery.
 11. An apparatus for wireless power transfer from a transmitting side to a receiving side, the apparatus comprising: an excitation power source generating a source field pattern energy at the transmitting side; a transmitting side near-field plate generating a subwavelength field pattern energy when excited by the excitation source, wherein after traversing a near-field distance, L, the source field pattern energy and the subwavelength field pattern energy form a desired field pattern energy at a focal plane, wherein the desired field pattern energy has a unidirectional subwavelength field pattern when the amplitude of the subwavelength field pattern is increased; and a power receiver and a receiving side near-field plate at the receiving side, the receiving side near-field plate being positioned at the focal plane and spaced a distance from the power receiver to couple a received energy from desired field pattern energy to the power receiver, wherein the power receiver is configured to convert the received energy into a received power for provision to a load.
 12. The apparatus of claim 11, wherein the excitation power source is a transmitting loop and wherein the power receiver is a receiving loop.
 13. The apparatus of claim 12, wherein the transmitting side near-field plate has the same configuration as the receiving side near field plate.
 14. The apparatus of claim 12, wherein the transmitting side near-field plate has a different configuration than the receiving side near field plate.
 15. The apparatus of claim 12, wherein the transmitting side near-field plate is formed of a plurality of concentric loops.
 16. The apparatus of claim 12, wherein the receiving side near-field plate is formed of a plurality of concentric loops.
 17. The apparatus of claim 12, wherein the transmitting loop comprises a Würth coil; and the receiving loop comprises a Würth coil.
 18. The apparatus of claim 12, further wherein the load is a device to receive the received power for wirelessly powering the device or wirelessly charging the device, wherein the device includes one or more of a computer, a smartphone, a biometric sensor device, a chargeable battery, or a vehicle using a chargeable battery. 